Space time spreading and phase sweep transmit diversity

ABSTRACT

Described herein is a method and apparatus for transmission that provides the performance of space time spreading (STS) or orthogonal transmit diversity (OTD) and the backwards compatibility of phase sweep transmit diversity (PSTD) without significantly degrading performance in additive white guassan noise (AWGN) conditions using a transmission architecture that incorporates STS/OTD and a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD, which involves transmitting a signal and a frequency swept version of the same signal over diversity antennas at different power levels to reduce the depths of nulls normally seen in AWGN conditions when regular PSTD is utilized.

RELATED APPLICATION

Related subject matter is disclosed in the following applications filed concurrently and assigned to the same assignee hereof: U.S. patent application Ser. No. 09/18392 entitled, “Symmetric Sweep Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buehrer, Paul A. Polakos and Mark Kraml; U.S. patent application Ser. No. 09/918393 entitled, “Biased Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buehrer and Robert Atmaram Soni; and U.S. patent application Ser. No. 09/918086 entitled, “Split Shift Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buehrer, Robert Atmaram Soni and Paul A. Polakos.

BACKGROUND OF THE RELATED ART

Performance of wireless communication systems is directly related to signal strength statistics of received signals. Third generation wireless communication systems utilize transmit diversity techniques for downlink transmissions (i.e., communication link from a base station to a mobile-station) in order to improve received signal strength statistics and, thus, performance. Two such transmit diversity techniques are space time spreading (STS) and phase sweep transmit diversity (PSTD).

FIG. 1 depicts a wireless communication system 10 employing STS. Wireless communication system 10 comprises at least one base station 12 having two antenna elements 14-1 and 14-2, wherein antenna elements 14-1 and 14-2 are spaced far apart for achieving transmit diversity. Base station 12 receives a signal S for transmitting to mobile-station 16. Signal S is alternately divided into signals s_(e) and s_(o), wherein signal s_(e) comprises even data bits and signal s_(o) comprises odd data bits. Signals s_(e) and s_(o) are processed to produce signals S¹⁴⁻¹ and S¹⁴⁻². Specifically, s_(e) is multiplied with Walsh code w₁ to produce signal s_(e)w₁; a conjugate of signal s_(o) is multiplied with Walsh code w₂ to produce signal s_(o)*w₂; signal s_(o) is multiplied with Walsh code w₁ to produce s_(o)w₁; and a conjugate of signal s_(e) is multiplied with Walsh code w₂ to produce s_(e)*w₂. Signal s_(e)w₁ is added to signal s_(o)*w₂ to produce signal S¹⁴⁻¹ (i.e., S¹⁴⁻¹=s_(e)w₁+s_(o)*w₂) and signal s_(e)*w₂ is subtracted from signal s_(o)w₁ to produce signal S¹⁴⁻² (i.e., S¹⁴⁻²=s_(o)w₁−s_(e)*w₂). Signals S¹⁴⁻¹ and S¹⁴⁻² are transmitted at substantially equal or identical power levels over antenna elements 14-1 and 14-2, respectively. For purposes of this application, power levels are “substantially equal” or “identical” when the power levels are within 1% of each other.

Mobile-station 16 receives signal R comprising γ₁(S¹⁴⁻²)+γ₂(S¹⁴⁻²), wherein γ₁ and γ₂ are distortion factor coefficients associated with the transmission of signals S¹⁴⁻¹ and S¹⁴⁻² from antenna elements 14-1 and 14-2 to mobile-station 16, respectively. Distortion factor coefficients γ₁ and γ₂ can be estimated using pilot signals, as is well-known in the art. Mobile-station 16 decodes signal R with Walsh codes w₁ and w₂ to respectively produce outputs: W ₁=γ₁ s _(e)+γ₂ s _(o)   equation 1 W ₂=γ₁ s _(o)*−γ₂ s _(e)*   equation 1a Using the following equations, estimates of signals s_(e) and s_(o), i.e., ŝ_(e) and ŝ_(o), may be obtained: ŝ _(e)=γ₁ ^(*) W ₁−γ₂ W ₂ ^(*) =s _(e)(|γ₁|²+|γ₂|²)+noise   equation 2 ŝ _(o)=γ₂ ^(*) W ₁+γ₁ W ₂ ^(*) =s _(o)(|γ₁|²+|γ₂|²)+noise′  equation 2a

However, STS is a transmit diversity technique that is not backward compatible from the perspective of the mobile-station. That is, mobile-station 16 is required to have the necessary hardware and/or software to decode signal R. Mobile-stations without such hardware and/or software, such as pre-third generation mobile-stations, would be incapable of decoding signal R.

By contrast, phase sweep transmit diversity (PSTD) is backward compatible from the perspective of the mobile-station. FIG. 2 depicts a wireless communication system 20 employing PSTD. Wireless communication system 20 comprises at least one base station 22 having two antenna elements 24-1 and 24-2, wherein antenna elements 24-1 and 24-2 are spaced far apart for achieving transmit diversity. Base station 22 receives a signal S for transmitting to mobile-station 26. Signal S is evenly power split into signals s₁ and s₂ and processed to produce signals S²⁴⁻¹ and S²⁴⁻², where s₁=s₂. Specifically, signal s₁ is multiplied by Walsh code w_(k) to produce S²⁴⁻¹=s₁w_(k), where k represents a particular user or mobile-station. Signal s₂ is multiplied by Walsh code w_(k) and a phase sweep frequency signal e^(j2πf) ^(s) ^(t) to produce S²⁴⁻², i.e., S²⁴⁻²=s₂w_(k)e^(j2πf) ^(s) ^(t)=s₁w_(k)e^(j2πf) ^(s) ^(t)=S²⁴⁻¹e^(j2πf) ^(s) ^(t), where f_(s) is a phase sweep frequency and t is time. Signals S²⁴⁻¹ and S²⁴⁻² are transmitted at substantially equal power levels over antenna elements 24-1 and 24-2, respectively. Note that the phase sweep signal e^(j2πf) ^(s) ^(t) is being represented in complex baseband notation, i.e., e^(j2πf) ^(s) ^(t)=cos(2πf_(s)t)+j sin(2πf_(s)t). It should be understood that the phase sweep signal may also be applied at an intermediate frequency or a radio frequency.

Mobile-station 26 receives signal R comprising γ₁S²⁴⁻¹+γ₂S²⁴⁻². Simplifying the equation for R results in R=γ ₁ S ²⁴⁻¹+γ₂ S ²⁴⁻¹ e ^(j2πf) ^(s) ^(t)   equation 3 R=S ²⁴⁻¹{γ₁+γ₂ e ^(j2πf) ^(s) ^(t)}  equation 3a R=S²⁴⁻¹γ_(eq)   equation 3b where γ_(eq) is an equivalent channel seen by mobile-station 26. Distortion factor coefficient γ_(eq) can be estimated using pilot signals and used, along with equation 3b, to obtain estimates of signal s₁ and/or s₂.

In slow fading channel conditions, both transmit diversity techniques, i.e., STS and PSTD, improve performance (relative to when no transmit diversity technique is used) by making the received signal strength statistics associated with a slow fading channel at the receiver look like those associated with a fast fading channel. However, PSTD does not provide the same amount of overall performance improvement as STS. Additionally, in additive white gaussan noise (AWGN) conditions, PSTD can significantly degrade performance, whereas STS neither improves nor degrades performance. Accordingly, there exists a need for a transmission technique that provides the performance of STS and the backwards compatibility of PSTD without significantly degrading performance in AGWN conditions.

SUMMARY OF THE INVENTION

The present invention is a method and apparatus for transmission that provides the performance of space time spreading (STS) or orthogonal transmit diversity (OTD) and the backwards compatibility of phase sweep transmit diversity (PSTD) without significantly degrading performance in additive white guassan noise (AWGN) conditions using a transmission architecture that incorporates STS/OTD and a form of PSTD referred to herein as biased PSTD, which involves transmitting a signal and a frequency swept version of the same signal over diversity antennas at different power levels to reduce the depths of nulls normally seen in AWGN conditions when PSTD is utilized.

In one embodiment, a signal s₁ comprising a non-STS/OTD signal and a first STS/OTD signal belonging to an STS/OTD pair is split into two signals s₁(a) and s₁(b), wherein the power level of signal s₁(a) is higher than the power level of signal s₁(b). The signal s₁(b) is phase swept using a phase sweep frequency signal. Thus, signal s₁ is processed in accordance with biased PSTD. The phase swept signal s₁(b) is added to a signal s₂ to produce a summed signal, wherein signal s₂ comprises a second STS/OTD signal belonging to the STS/OTD pair. The summed signal and the signal s₁(a) are amplified and transmitted over a pair of diversity antennas. The amount of gain applied to the summed signal and the signal s₁(a) may be equal or unequal such that the amplified summed signal and the amplified signal s₁(a) are at approximately equal power levels.

BRIEF DESCRIPTION OF THE DRAWINGS

The features, aspects, and advantages of the present invention will become better understood with regard to the following description, appended claims, and accompanying drawings where

FIG. 1 depicts a wireless communication system employing space time spreading techniques in accordance with the prior art;

FIG. 2 depicts a wireless communication system employing phase sweep transmit diversity in accordance with the prior art;

FIG. 3 depicts a base station employing code division multiple access (CDMA), a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD, and space time spreading (STS) or orthogonal transmit diversity (OTD) in accordance with one embodiment of the present invention;

FIG. 4 depicts a base station employing CDMA, biased PSTD, and STS or OTD in accordance with another embodiment of the present invention; and

FIG. 5 depicts a base station employing CDMA, biased PSTD, STS or OTD, and split shift PSTD in accordance with another embodiment of the present invention.

DETAILED DESCRIPTION

FIG. 3 depicts a base station 30 employing code division multiple access (CDMA), a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD, and space time spreading (STS) or orthogonal transmit diversity (OTD) in accordance with the present invention. CDMA, PSTD, STS and OTD are well-known in the art.

Base station 30 provides wireless communication services to mobile-stations, not shown, in its associated geographical coverage area or cell, wherein the cell is divided into three sectors α, β, γ. Base station 30 includes a transmission architecture that incorporates STS or OTD and biased PSTD, as will be described herein.

Base station 30 comprises a processor 32, a splitter 34, multipliers 36, 38, 40, adder 42, amplifiers 44, 46, and a pair of diversity antennas 48, 50. Note that base station 30 also includes configurations of splitters, multipliers, adders, amplifiers and antennas for sectors β, γ that are identical to those for sector α. For simplicity sake, the configuration for sectors β, γ are not shown. Additionally, for discussion purposes, it is assumed that signals S_(k) are intended for mobile-stations k located in sector α and, thus, the present invention will be described with reference to signals S_(k) being processed for transmission over sector α.

Processor 32 includes software for processing signals S_(k) in accordance with well-known CDMA and STS/OTD techniques, where STS/OTD indicates STS and/or OTD. The manner in which a particular signal S_(k) is processed by processor 32 depends on whether mobile-station k is STS/OTD compatible, i.e., mobile-station capable of decoding signals processed using STS/OTD. Processor 32 may also include software for determining whether mobile-station k is STS/OTD compatible. If mobile-station k is not STS/OTD compatible, then signal S_(k) is processed in accordance with CDMA techniques to produce signal S_(k-1), which is also referred to herein as a non-STS/OTD signal S_(k-1).

Note that, in another embodiment, processor 32 is operable to process signals S_(k) in accordance with a multiple access technique other than CDMA, such as time or frequency division multiple access. In this embodiment, when mobile-station k is not STS/OTD compatible, then signal S_(k) is processed in accordance with such other multiple access technique to produce the non-STS/OTD signal S_(k-1).

If mobile-station k is STS/OTD compatible, then signal S_(k) is processed in accordance with CDMA and STS/OTD. Specifically, if mobile-station k is STS compatible, then signal S_(k) is processed using STS. Such process includes alternately dividing signal S_(k) into signals s_(e) and s_(o), wherein signal s_(e) comprises even data bits and signal s_(o) comprises odd data bits. Signal s_(e) is multiplied with Walsh code w₁ to produce signal s_(e)w₁, and a conjugate of signal s_(e) is multiplied with Walsh code w₂ to produce s_(e)*w₂. Signal s_(o) is multiplied with Walsh code w₁ to produce s_(o)w₁, and a conjugate of signal s_(o) is multiplied with Walsh code w₂ to produce signal s_(o)*w₂. Signal s_(e)w₁ is added to signal s_(o)*w₂ to produce signal S_(k-2)(a)=s_(e)w₁+s_(o)*w₂. Signal s_(e)*w₂ is subtracted from signal s_(o)w₁ to produce signal S_(k-2)(b)=s_(o)w₁−s_(e)*w₂). Signals S_(k-2)(a), S_(k-2)(b) are also referred to herein as STS signals, and together signals S_(k-2)(a), S_(k-2)(b) collectively comprise an STS pair.

If mobile-station k is OTD compatible, then signal S_(k) is processed using OTD. Orthogonal transmit diversity involves dividing signal S_(k) into signals s_(e) and s_(o), and multiplying signals s_(e) and s_(o) using Walsh codes w₁, w₂ to produce signals S_(k-3)(a), S_(k-3)(b), i.e., S_(k-3)(a)=s_(e)w₁ and S_(k-3)(b)=s_(o)w₂, respectively. Signals S_(k-3)(a), S_(k-3)(b) are also referred to herein as OTD signals, and together signals S_(k-3)(a), S_(k-3)(b) collectively comprise an OTD pair.

For illustration purposes, the present invention will be described herein with reference to STS and signals S_(k-2)(a), S_(k-2)(b). It should be understood that the present invention is also applicable to OTD and signals S_(k-3)(a), S_(k-3)(b).

The output of processor 32 are signals s_(α-1), s_(α-2), where signal s_(α-1) comprises of signals S_(k-1) and S_(k-2)(a) and signal s_(α-2) comprises of signals S_(k-2)(b), i.e., S_(α-1)=ΣS_(k-1)+ΣS_(k-2)(a) and s_(α-2)=ΣS_(k-2)(b). That is, signals intended for STS compatible mobile-stations are included in both output signals s_(α-1), s_(α-2) and signals intended for non-STS compatible mobile-stations are included in only signal s_(α-1). Alternately, signal s_(α-1) comprises of signals S_(k-1) and S_(k-2)(b) and signal s_(α-2) comprises of signals S_(k-2)(a).

Signal s_(α-1) is split by splitter 34 into signals s_(α-1)(a), s_(α-1)(b) and processed along paths A and B, respectively, by multipliers 36, 38, 40, adder 42 and amplifiers 44, 46 in accordance with bias PSTD techniques. Basically, biased PSTD involves transmitting a signal and a frequency swept version of the same signal over diversity antennas at different power levels. Advantageously, biased PSTD is backwards compatible from the perspective of mobile-stations and does not degrade performance as much as PSTD in additive white gaussan noise (AWGN) conditions.

In one embodiment, signal s_(α-1) is unevenly power split by splitter 34 such that the power level of signal s_(α-1)(a) is higher than the power level of signal s_(α-1)(b). For example, signal s_(α-1) is power split such that signal s_(α-1)(a) gets ⅝ of signal s_(α-1)'s power and signal s_(α-1)(b) gets ⅜ of signal s_(α-1)'s power, i.e., s_(α-1)(a)=√{square root over (⅝)} (s_(α-1)) and s_(α-1)(b)=√{square root over (⅜)} (s_(α-1)). In another example, signal s_(α-1) is power split such that signal s_(α-1)(a) gets ⅔ of signal s_(α-1)'s power and signal s_(α-1)(b) gets ⅓ of signal s_(α-1)'s power. In another embodiment, signal s_(α-1) is evenly power split by splitter 34. Note that signal s_(α-1)(a) is identical to signal s_(α-1)(b) in terms of data. Signal s_(α-1)(a) and carrier signal e^(−j2πf) ^(c) ^(t) are provided as inputs into multiplier 36 to produce signal S₃₆, where S₃₆=s_(α-1)(a)e^(−j2πf) ^(c) ^(t), e^(−j2πf) ^(c) ^(t)=cos(2πf_(c)t)+j sin(2πf_(c)t), f_(c) represents a carrier frequency and t represents time.

Signal s_(α-1)(b) and phase sweep frequency signal e^(−jΘ) ³ ^((t)) are provided as inputs into multiplier 38 where signal s_(α-1)(b) is frequency phase swept with signal e^(−jΘ) ^(s) ^((t)) to produce signal S₃₈=s_(α-1)(b)e^(−jΘ) ^(s) ^((t)), wherein Θ_(s)=2πf_(s)t, e^(−jΘ) ^(s) ^((t))=cos(2πf_(s)t)+j sin(2πf_(s)t) and f_(s) represents a phase sweep frequency.

Signal S₃₈ is added to signal s_(α-2) by adder 42 to produce signal S₄₂=s_(α-1)(b)e^(−jΘ) ^(s) ^((t))+s_(α-2). Signal S₄₂ and carrier signal e^(−j2πf) ^(c) ^(t) are provided as inputs into multiplier 40 to produce signal S₄₀, where S₄₀=(s_(α-1)(b)e^(−jΘ) ^(s) ^((t))+s_(α-2))e^(−j2πf) ^(c) ^(t).

Signals S₃₆, S₄₀ are amplified by amplifiers 44, 46 to produce signals S₄₄ and S₄₆ for transmission over antennas 48, 50, respectively, where signal S₄₄=A₄₄s_(α-1)(a)e^(−j2πf) ^(c) ^(t), S₄₆=A₄₆(s_(α-1)(b)e^(−jΘ) ^(s) ^((t))+s_(α-2))e^(−j2πf) ^(c) ^(t), A₄₄ represents the amount of gain associated with amplifier 44 and A₄₆ represents the amount of gain associated with amplifier 46.

In one embodiment, the amounts of gain A₄₄, A₄₆ are equal. In this embodiment, signal s_(α-1) is split by splitter 34 such that the power level of signal s_(α-1)(a) is higher than the power level of signal s_(α-1)(b) so that differences in power level between signals S₄₄ and S₄₆ are not as large compared to an even power split of signal s_(α-1).

In another embodiment, the amounts of gain A₄₄, A₄₆ are different and related to how splitter 34 power splits signal s_(α-1). Specifically, the amount of gain A₄₄, A₄₆ applied to signals S₃₆, S₄₀ should be an amount that would cause the power levels of signals S₄₄ and S₄₆ to be approximately equal. For purposes of this application, power levels are “approximately equal” when the power levels are within 10% of each other. For example, suppose the power levels of both signals s_(α-1), s_(α-2) are x and splitter 34 splits signal s_(α-1) such that the power levels of signals s_(α-1)(a), s_(α-1)(b) are 7/8x and 1/8x, respectively. After signal signals s_(α-2)is added to signal S₃₈ by adder 42, the power level of the resultant signal S₄₂ is 9/8x. In this example, the amount of gains A₄₄, A₄₆ might be 8/7 and 8/9, respectively.

In the case where signal s_(α-1) and/or signals S₃₆, S₄₀ are not biased or unevenly split or amplified, STS performance will degrade because signal S₄₄ will be transmitted at approximately ⅓ of the power at which signal S₄₆ will be transmitted. Advantageously, biasing or unevenly splitting signal s_(α-1) and/or biasing or unevenly amplifying signals S₃₆, S₄₀ mitigates this degradation to STS performance relative to the case where neither signal s_(α-1) nor signals S₃₆, S₄₀ are biased or unevenly split or amplified.

FIG. 5 depicts a base station 70 employing CDMA, biased PSTD, STS/OTD and split shift PSTD in accordance an embodiment of the present invention. In this embodiment, , a form of PSTD referred to herein as split shift PSTD in also utilized. Spilt shift PSTD involves shifting both signals split from a single signal using phase sweep frequency signals that sweeps both signals in opposite direction. As shown in FIG. 5, signals s_(α-1)(a), is phase swept by multiplier 39 using phase sweep frequency signals e^(jΘ) ^(s) ^((t)). Although this embodiment depicts phase sweep frequency signal e^(jΘ) ^(s) ^((t)) equal and opposite to phase sweep frequency signals e^(−jΘ) ^(s) ^((t)), it should be understood that the phase sweep frequency signal used to phase sweep signals s_(α-1)(a) need not be equal in magnitude. In another embodiment, signal s_(α-1)(a) is phase swept using a phase sweep frequency signal that results in phase swept signal s_(α-1)(a) with a desired or other phase difference to phase swept signal s_(α-1)(b). Note that that the phase sweep frequency signal used to phase sweep signals s_(α-1)(a), s_(α-1)(b) may be phase shifting at an identical or different rate from each other, may be phase shifting at fixed and/or varying rates, or may be phase shifting in the same or opposite direction.

Although the present invention has been described in considerable detail with reference to certain embodiments, other versions are possible. For example, phase sweeping may be performed along path A instead of path B, i.e., signal s_(α-1)(a) is phase swept with signal e^(−jΘ) ^(s) ^((t)). FIG. 4 depicts a base station 60 in which phase sweeping is performed along path A instead of path B. Therefore, the spirit and scope of the present invention should not be limited to the description of the embodiments contained herein. 

1. A method of signal transmission comprising the steps of: splitting a signal s₁ into signals s₁(a) and s₁(b), wherein signal s₁ comprises a first STS/OTD signal belonging to an STS/OTD pair; phase sweeping the signal s₁(b) using a first phase sweep frequency signal to produce a phase swept signal s₁(b); and adding the phase swept signal s₁(b) to a signal s₂ to produce a summed signal s₃, wherein the signal s₂ comprises a second STS/OTD signal belonging to the STS/OTD pair.
 2. The method of claim 1, wherein the signal s₁ is split unevenly such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b).
 3. The method of claim 1 comprising the additional steps of: amplifying the signal s₁(a) to produce an amplified signal s₁(a); and amplifying the signal s₃ to produce an amplified signal s₃.
 4. The method of claim 3, wherein power levels associated with the amplified signal s₁(a) and the amplified signal s₃ are approximately equal.
 5. The method of claim 3, wherein the signals s₁(a) and s₃ are amplified an equal amount.
 6. The method of claim 1 comprising the additional steps of: transmitting the signal s₁(a) over a first antenna belonging to a pair of diversity antennas; and transmitting the signal s₃ over a second antenna belonging to the pair of diversity antennas.
 7. The method of claim 1 comprising the additional steps of: processing a signal S using space time spreading techniques to produce the signals s₁ and s₂.
 8. The method of claim 1, wherein the signal s₁ comprises a non-STS/OTD signal.
 9. The method of claim 1 comprising the additional steps of: phase sweeping the signal s₁(a) using a second phase sweep frequency signal to produce a phase swept signal s₁(a) with a different phase from the phase swept signal s₁(b).
 10. A method of signal transmission comprising the steps of: splitting a signal s₁ into signals s₁(a) and s₁(b), wherein signal s₁ comprises a first STS/OTD signal belonging to an STS/OTD pair; phase sweeping the signal s₁(a) using a first phase sweep frequency signal to produce a phase swept signal s₁(a); and adding the signal s₁(b) to a signal s₂ to produce a summed signal s₃, wherein the signal s₂ comprises a second STS/OTD signal belonging to the STS/OTD pair.
 11. The method of claim 10, wherein the signal s₁ is split unevenly such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b).
 12. The method of claim 10 comprising the additional steps of: amplifying the phase swept signal s₁(a) to produce an amplified phase swept signal s₁(a); and amplifying the signal s₃ to produce an amplified signal s₃.
 13. The method of claim 12, wherein power levels associated with the amplified phase swept signal s₁(a) and the amplified signal s₃ are approximately equal.
 14. The method of claim 12, wherein the phase swept signal s₁(a) and the signal s₃ are amplified an equal amount.
 15. The method of claim 10 comprising the additional steps of: transmitting the phase swept signal s₁(a) over a first antenna belonging to a pair of diversity antennas; and transmitting the signal s₃ over a second antenna belonging to the pair of diversity antennas.
 16. The method of claim 10 comprising the additional steps of: processing a signal S using space time spreading techniques to produce the signals s₁ and s₂.
 17. The method of claim 10, wherein the signal s₁ comprises a non-STS/OTD signal.
 18. The method of claim 10 comprising the additional steps of: phase sweeping the signal s₁(b) using a second phase sweep frequency signal to produce a phase swept signal s₁(b) with a different phase from the phase swept signal s₁(a).
 19. A base station comprising: a splitter for splitting a signal s₁ into signals s₁(a) and s₁(b), wherein signal s₁ comprises a first STS/OTD signal belonging to an STSOTD pair; a multiplier for phase sweeping the signal s₁(b) using a first phase sweep frequency signal to produce a phase swept signal s₁(b); and an adder for adding the phase swept signal s₁(b) to a signal s₂ to produce a summed signal s₃, wherein the signal s₂ comprises a second STS/OTD signal belonging to the STS/OTD pair.
 20. The base station of claim 19, wherein the splitter unevenly splits the signal s₁ such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b).
 21. The base station of claim 19 further comprising: a first amplifier for amplifying the signal s₁(a) to produce an amplified signal s₁(a); and a second amplifier for amplifying the signal s₃ to produce an amplified signal s₃.
 22. The base station of claim 21, wherein the first and second amplifiers amplify the signals s₁(a) and s₃ such that power levels associated with the amplified signals s₁(a) and s₃ are approximately equal.
 23. The base station of claim 21, wherein the first and second amplifiers amplify the signals s₁(a) and s₃ an equal amount.
 24. The base station of claim 19 further comprising: a pair of diversity antennas having a first and a second antenna; a first transmitter for transmitting the signal s₁(a) over the first antenna; and a second transmitter for transmitting the signal s₃ over the second antenna.
 25. The base station of claim 19 further comprising: a processor for processing a signal S using STS/OTD techniques to produce the signals s₁ and s₂.
 26. The base station of claim 19, wherein the signal s₁ comprises a non-STS/OTD signal.
 27. The base station of claim 19 further comprising: a multiplier for phase sweeping the signal s₁(a) using a second phase sweep frequency signal to produce a phase swept signal s₁(a) with a different phase from the phase swept signal s₁(b).
 28. A base station comprising: a splitter for splitting a signal s₁ into signals s₁(a) and s₁(b), wherein signal s₁ comprises a first STS/OTD signal belonging to an STS/OTD pair; a multiplier for phase sweeping the signal s₁(a) using a first phase sweep frequency signal to produce a phase swept signal s₁(a); and an adder for adding the signal s₁(b) to a signal s₂ to produce a summed signal s₃, wherein the signal s₂ comprises a second STS/OTD signal belonging to the STS/OTD pair.
 29. The base station of claim 28, wherein the splitter unevenly splits the signal s₁ such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b).
 30. The base station of claim 28 further comprising: a first amplifier for amplifying the phase swept signal s₁(a) to produce an amplified phase swept signal s₁(a); and a second amplifier for amplifying the signal s₃ to produce an amplified signal s₃.
 31. The base station of claim 30, wherein the first and second amplifiers amplify the signals s₁(a) and s₃ such that power levels associated with the amplified phase swept signal s₁(a) and amplified signal s₃ are approximately equal.
 32. The base station of claim 30, wherein the first and second amplifiers amplify the signals s₁(a) and s₃ an equal amount.
 33. The base station of claim 28 further comprising: a pair of diversity antennas having a first and a second antenna; a first transmitter for transmitting the phase swept signal s₁(a) over the first antenna; and a second transmitter for transmitting the signal s₃ over the second antenna.
 34. The base station of claim 28 further comprising: a processor for processing a signal S using space time spreading techniques to produce the signals s₁ and s₂.
 35. The base station of claim 28, wherein the signal s₁ comprises a non-STS/OTD signal.
 36. The base station of claim 28 further comprising: a multiplier for phase sweeping the signal s₁(b) using a second phase sweep frequency signal to produce a phase swept signal s₁(b) with a different phase from the phase swept signal s₁(a). 